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MT9196 Integrated Digital Phone Circuit (IDPC)
Data Sheet Features
* * * * * * * * * * Programmable m-Law/A-Law CODEC and Filters Programmable CCITT (G.711)/sign-magnitude coding Programmable transmit, receive and side-tone gains Digital DTMF and single tone generation Fully differential interface to handset transducers Auxiliary analog interface Interface to ST-BUS/SSI (compatible with GCI) Serial microport control Single 5 volt supply, low power operation Anti-howl circuit for group listening speakerphone applications The MT9196 Integrated Digital Phone Circuit (IDPC) is designed for use in digital phone products. The device incorporates a built-in Filter/Codec, digital gain pads, DTMF generator and tone ringer. Complete telephony interfaces are provided for connecting to handset and speakerphone transducers. Internal register access is provided through a serial microport compatible with various industry standard micro-controllers. The device is fabricated in Zarlink's ISO2-CMOS technology ensuring low power consumption and high reliability.
Filter/Codec Gain Encoder Decoder 7dB -7dB Transducer Interface
January 2006
ISO2-CMOS
Ordering Information MT9196AP 28 Pin PLCC Tubes MT9196AE 28 Pin PDIP Tubes MT9196AS 28 Pin SOIC Tubes MT9196ASR 28 Pin SOIC Tape & MT9196APR 28 Pin PLCC Tape & MT9196AE1 28 Pin PDIP* Tubes MT9196APR1 28 Pin PLCC* Tape & MT9196AP1 28 Pin PLCC* Tubes MT9196AS1 28 Pin SOIC* Tubes MT9196ASR1 28 Pin SOIC* Tape & *Pb Free Matte Tin -40C to +85C
Reel Reel Reel Reel
Description
Applications
* * * Digital telephone sets Wireless telephones Local area communications stations
Digital Gain & Tone Generator VSSD VDD VSSA VSS SPKR VBias VRef 21/ - 24dB 3.0dB Tx & Rx
AUXin AUXout MIC + MM+
HSPKR + HSPKR Din Timing Dout STB/F0i CLOCKin Serial Microport XSTL2 IC IRQ CS DATA1 DATA2 SCLK Flexible Digital Interface SPKR + SPKR -
ST-BUS C&D Channels
WD
PWRST
Figure 1 - Functional Block Diagram 1
Zarlink Semiconductor Inc. Zarlink, ZL and the Zarlink Semiconductor logo are trademarks of Zarlink Semiconductor Inc. Copyright 1995-2005, Zarlink Semiconductor Inc. All Rights Reserved.
MT9196
Data Sheet
M+ MVSSA MIC+ AUXin
VRef VBias
PWRST IC VSSD CS SCLK DATA1 DATA2
4 3 2 1 28 27 26 5 25 24 6 7 23 22 8 21 9 20 10 11 19 12 13 14 15 16 17 18
AUXout VSS SPKR SPKR+ SPKRHSPKR+ HSPKRVDD
WD IRQ Dout Din STB/F0i CLOCKin XSTAL2
MM+ VBias VRef PWRST IC VSSD CS SCLK DATA1 DATA2 WD IRQ Dout
1 2 3 4 5 6 7 8 9 10 11 12 13 14
28 27 26 25 24 23 22 21 20 19 18 17 16 15
VSSA MIC+ AUXin AUXout VSS SPKR SPKR+ SPKRHSPKR+ HSPKRVDD XSTAL2 CLOCKin STB/F0i Din
28 PIN PLCC
28 PIN SOIC/PDIP Figure 2 - Pin Connections
Pin Description Pin # 1 2 3 4 5 6 7 8 9 10 Name MM+ VBias VRef PWRST IC VSSD CS SCLK DATA1 Description Inverting Microphone (Input). Inverting input to microphone amplifier from the handset microphone. Non-Inverting Microphone (Input). Non-inverting input to microphone amplifier from the handset microphone. Bias Voltage (Output). (VDD/2) volts is available at this pin for biasing external amplifiers. Connect 0.1 F capacitor to VSSA. Reference voltage for codec (Output). Nominally [(VDD/2)-1.5] volts. Used internally. Connect 0.1 F capacitor to VSSA. Power-up Reset (Input). CMOS compatible input with Schmitt Trigger (active low). Internal Connection. Tie externally to VSS for normal operation. Digital Ground. Nominally 0 volts. Chip Select (Input). This input signal is used to select the device for microport data transfers. Active low. TTL level compatible. Serial Port Synchronous Clock (Input). Data clock for microport. TTL level compatible. Bidirectional Serial Data. Port for microprocessor serial data transfer. In Motorola/National mode of operation, this pin becomes the data transmit pin only and data receive is performed on the DATA2 pin. TTL level compatible input levels. Serial Data Receive. In Motorola/National mode of operation, this pin is used for data receive to the IDPC. In Intel mode, serial data transmit and receive are performed on the DATA1 pin and DATA2 is disconnected. Input level TTL compatible. Watchdog (Output). Watchdog timer output. Active high. Interrupt Request (Open Drain Output). Low true interrupt output to microcontroller.
11
DATA2
12 13
WD
IRQ
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MT9196
Pin Description (continued) Pin # 14 Name Dout Description
Data Sheet
Data Output. A tri-state digital output for 8 bit wide channel data being sent to the Layer 1 device. Data is shifted out via this pin concurrent with the rising edge of BCL during the timeslot defined by STB, or according to standard ST-BUS timing. Data Input. A digital input for 8 bit wide channel data received from the Layer 1 device. Data is sampled on the falling edge of BCL during the timeslot defined by STB, or according to standard ST-BUS timing. Input level is CMOS compatible. Data Strobe/Frame Pulse (Input). For SSI mode this input determines the 8 bit timeslot used by the device for both transmit and receive data. This active high signal has a repetition rate of 8 kHz. Standard frame pulse definitions apply in ST-BUS mode. CMOS level compatible input.
15
Din
16
STB/F0i
17
CLOCKin Clock Input. The clock provided to this input is used by the internal phone functions. In STBUS mode this is the C4i input. In SSI synchronous mode, this is the Bit Clock input. In SSIasynchronous mode this is an asynchronous 4 MHz Master Clock input. XSTL2 VDD Crystal Input (4.096 MHz). Used in conjunction with the CLOCKin pin to provide the master clock signal via external crystal. Positive Power Supply (Input). Nominally 5 volts.
18 19 20 21 22 23 24 25 26 27 28
HSPKR- Inverting Handset Speaker (Output). Output to the handset speaker (balanced). HSPKR+ Non-Inverting Handset Speaker (Output). Output to the handset speaker (balanced). SPKRSPKR+ Inverting Speaker (Output). Output to the speakerphone speaker (balanced). Non-Inverting Speaker (Output). Output to the speakerphone speaker (balanced).
VSSSPKR Power Supply Rail for Speaker Driver. Nominally 0 Volts. AUXout AUXin MIC+ VSSA Auxiliary Port (Output). Access point to the D/A (analog) signals of the receive path as well as to the various analog inputs. Auxiliary Port (Input). An analog signal may be fed to the filter/codec transmit section and various loopback paths via this pin. No external anti-aliasing is required. Non-inverting on-hook answer back Microphone (Input). Microphone amplifier noninverting input pin. Analog Ground (Input). Nominally 0 V.
Overview
The functional block diagram of Figure 1 depicts the main operations performed by the MT9196 IDPC. Each of these functional blocks will be described individually in the sections to follow. This overview will describe some of the end-user features which may be implemented as a direct result of the level of integration found within the IDPC. The main feature required of a digital telephone is to convert the digital Pulse Code Modulated (PCM) information, being received by the telephone set, into an analog electrical signal. This signal is then applied to an appropriate audio transducer such that the information is finally converted into intelligible acoustic energy. The same is true of the reverse direction where acoustic energy is converted first into an electrical analog and then digitized (into PCM) before being transmitted from the set. Along the way if the signals can be manipulated, either in the analog or the digital domains, other features such as gain control and signal generation may be added. Finally, most electroacoustic transducers (loudspeakers) require a large amount of power if they are to develop an acoustic signal. The inclusion of audio amplifiers to provide this power is required.
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Data Sheet
The IDPC features complete Analog/Digital and Digital/Analog conversion of audio signals (Filter/CODEC) and an analog interface to electro-acoustic devices (Transducer Interface). Full programmability of the receive path and side-tone gains is available to set comfortable listening levels for the user. Transmit path gain control is available for setting nominal transmit levels into the network. A digital, anti-feedback circuit permits both the handset microphone and the speaker-phone speaker to be enabled at the same time for group listening applications. This anti-feedback circuit limits the total loop gain there by preventing a singing condition from developing. Signalling in digital telephone systems, behind the PBX or standard ISDN applications, is handled on the D-channel and generally does not require DTMF tones. Locally generated tones, in the set, however, can be used to provided "comfort tones" or "key confirmation" to the user, similar to the familiar DTMF tones generated by conventional phones during initial call set-up. Also, as the network slowly evolves from the dial pulse/DTMF methods to the DChannel protocols it is essential that the older methods be available for backward compatibility. As an example, once a call has been established (i.e., from your office to your home) using the D-Channel signalling protocol it may be necessary to use in-band DTMF signalling to manipulate your personal answering machine in order to retrieve messages. Thus the locally generated tones must be of network quality. The IDPC can generate the required tone pairs as well as single tones to accommodate any in-band signalling requirement. Each of the programmable parameters within the functional blocks is accessed through a serial microcontroller port compatible with Intel MCS-51(R), Motorola SPI(R) and National Semiconductor Microwire(R) specifications.
Functional Description
In this section each of the functional blocks within IDPC is described along with all of the associated control/status bits. Each time a control/status bit(s) is described it is followed by the address register where it will be found. The reader is referred to the section titled 'Register Summary' for a complete listing of all address registers, the control/status bits associated with each register and a definition of the function of each control/status bit. The Register Summary is useful for future reference of control/status bits without the need to locate them in the text of the functional descriptions. Filter/CODEC The Filter/CODEC block implements conversion of the analog 3.3 kHz speech signals to/from the digital domain compatible with 64 kb/s PCM B-Channels. Selection of companding curves and digital code assignment are register programmable. These are CCITT G.711 A-law or -Law, with true-sign/ Alternate Digit Inversion or truesign/Inverted Magnitude coding, respectively. Optionally, sign- magnitude coding may also be selected for proprietary applications. The Filter/CODEC block also implements transmit and receive audio path gains in the analog domain. These gains are in addition to the digital gain pad section and provide an overall path gain resolution of 1.0 dB. A programmable gain, voice side-tone path is also included to provide proportional transmit speech feedback to the handset receiver. Figure 3 depicts the nominal half-channel and side-tone gains for the IDPC. On PWRST (pin 5) the Filter/CODEC defaults such that the side-tone path, dial tone filter and 400 Hz transmit filter are off, all programmable gains are set to 0 dB and CCITT -Law is selected. Further, the Filter/CODEC is powered down due to the control bits of the Path Control Registers (addresses 12h and 13h) being reset. The internal architecture is fully differential to provide the best possible noise rejection as well as to allow a wide dynamic range from a single 5 volt supply design. This fully differential architecture is continued into the Transducer Interface section to provide full chip realization of these capabilities for the handset and loudspeaker functions. A reference voltage (VRef), for the conversion requirements of the CODEC section, and a bias voltage (VBias), for biasing the internal analog sections, are both generated on-chip. VBias is also brought to an external pin so that it may be used for biasing external gain plan setting amplifiers. A 0.1 F capacitor must be connected from VBias to analog ground at all times. Likewise, although VRef may only be used internally, a 0.1 F capacitor from the VRef pin to ground is required at all times. The analog ground reference point for these two capacitors must be physically the same point. To facilitate this the VRef and VBias pins are situated on adjacent pins.
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Data Sheet
The transmit filter is designed to meet CCITT G.714 specifications. The nominal gain for this filter path is 0 dB (gain control = 0 dB). Gain control allows the output signal to be increased up to 7 dB. An anti-aliasing filter is included. This is a second order lowpass implementation with a corner frequency at 25 kHz. Attenuation is better than 32 dB at 256 kHz and less than 0.01 dB within the passband. An optional 400 Hz high-pass function may be included into the transmit path by enabling the Tfhp bit in the Control Register 1 (address 0Eh). This option allows the reduction of transmitted background noise such as motor and fan noise. SERIAL PORT DIGITAL GAIN & TONES FILTER/CODEC TRANSDUCER INTERFACE
-6.1 dB or -3.6 dB HSPKR + Receive Receiver Driver
75
Handset Receiver (150)
PCM
Din
-24 to +21 dB (3dB steps)
Receive Filter Gain 0 to -7 dB (1 dB steps)
-6 dB
HSPKR 75
Side-tone -9.96 to +9 96dB (3.32 dB steps) DTMF, Tone Ringer -11 dB
Speaker Phone Driver 0 dB
SPKR + SPKR -
0/+8dB +8 to -20dB (4 dB steps) RINGER 0 to -28 dB (4 dB steps) Auxiliary Out Driver -12 dB AUXout
Speakerphone Speaker (40 nominal) 34 min)
PCM
Dout
-24 to +21 dB (3 dB steps) Transmit
Transmit Filter Gain 0 to +7 dB (1 dB steps)
Transmit Gain -0.37 dB or 8.93 dB
Transmit Gain 6.37 dB
5 dB M U X 5 dB
AUXin AUX input MIC+ H/F answerback mic
M + Transmitter microphone M-
Digital Domain
Analog Domain
Internal To Device
External To Device
Figure 3 - Audio Gain Partitioning The receive filter is designed to meet CCITT G.714 specifications. The nominal gain for this filter path is 0 dB (gain control = 0dB). Gain control allows the output signal to be attenuated up to 7 dB. Filter response is peaked to compensate for the sinx/x attenuation caused by the 8 kHz sampling rate. The Rx filter function can be altered by enabling the Dial EN control bit in Control Register 1 (address 0Eh). This causes another low-pass function to be added with a 3 dB point at 1200 Hz. This function is intended to improve the sound quality of digitally generated dial tone received as PCM. Side-tone is derived from the Tx filter before the LP/HP filter section and is not subject to the gain control of the Tx filter section. Side-tone is summed into the receive handset transducer driver path after the Rx filter gain control
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Data Sheet
section so that Rx gain adjustment will not affect side-tone levels. The side-tone path may be enabled/disabled with the Voice sidetone bit located in the Receive Path Control Register (address 13h). Transmit and receive filter gains are controlled by the TxFG0-TxFG2 and RxFG0-RxFG2 control bits, respectively. These are located in the FCODEC Control Register 1 (address 0Ah). Transmit filter gain is adjustable from 0 dB to +7 dB and receive filter gain from 0 dB to -7 dB, both in 1 dB increments. Side-tone filter gain is controlled by the STG0-STG2 control bits located in the FCODEC Control Register 2 (address 0Bh). Side-tone gain is adjustable from -9.96 dB to +9.96 dB in 3.32 dB increments. Companding law selection for the Filter/CODEC is provided by the A/ companding control bit while the coding scheme is controlled by the sign-mag/CCITT control bit. Both of these reside in Control Register 2 (address 0Fh). Table 1 illustrates these choices. CCITT (G.711) -Law
1000 0000 1111 1111 0111 1111 0000 0000
Code
+ Full Scale + Zero -Zero (quiet code) - Full Scale
Sign/ Magnitude
1111 1111 1000 0000 0000 0000 0111 1111
A-Law
1010 1010 1101 0101 0101 0101 0010 1010
Table 1 The Filter/CODEC autonull circuit ensures that transmit PCM will contain no more than 1 bit of offset due to internal circuitry. Digital Gain and Tone Generation The Digital gain and Tone generator block is located, functionally, between the serial FDI port and the Filter/CODEC block. Its main function is to provide digital gain control of the transmit and receive audio signals and to generate digital patterns for DTMF and tone ringer signals. Gain Control Gain control is performed on linear code for both the receive and the transmit PCM. Gain control is set via the Digital Gain Control Register at address 19h. Gain, in 3.0 dB increments, is available within a range of +21.0 dB to -24 dB. DTMF Generator The digital DTMF circuit generates a dual sine-wave pattern which may be routed into the receive path as comfort tones or into the transmit path as network signalling. In both cases the digitally generated signal will undergo gain adjustment as programmed into the transmit and receive gain control registers. Gain control is assigned automatically as functions are selected via the transmit and receive path control registers. The composite signal output level in the transmit direction is -4 dBm0 (-Law) and -10 dBm0 (A-law) with programmable gains at zero dB. Pre-twist of 2.0 dB is incorporated into the composite signal resulting in a low tone output level of -8.12 dBm0 and a high group level of -6.12 dBm0 (for -Law, 6 dB lower for A-Law). Note that these levels will be influenced by the Anti-Howling circuit when it is enabled (see Anti-Howling section for more details). DTMF side-tone levels are set to -28 dBm0 from the generator circuit. Other receive path gains must be included when calculating the analog output signal levels. Adjustments to these levels may be made by altering the settings of the Gain Control register (address 19h).
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Data Sheet
The frequency of the low group tone is programmed by writing an 8-bit coefficient into the Low Tone Coefficient Register (address 1Ah) while the high group tone frequency uses the 8-bit coefficient programmed into the High Tone Coefficient Register (address 1Bh). Both coefficients are determined by the following equation: Frequency (in Hz) = 7.8125 x COEFF Where COEFF is an integer between 0 and 255. Frequency resolution is 7.8125 Hz in the range 0 to 1992 Hz. Low and high tones are enabled individually via the LoEn and HiEN control bits (DTMF/Ringer Control Register, address 18h). This not only provides control over dual tone generation but also allows single tone generation using either of the enable bits and its associated coefficient register. After programming and enabling the tone generators as described, selection of transmit and/or receive path destinations are carried out via the Path Control Registers (see Path Control section). In addition receive sidetone DTMF must be selected via the DTMF StEN bit (DTMF/Tone ringer Register, address 18h) so that it replaces the received PCM in the Rx Filter path. Frequency (Hz) 697 770 852 941 1209 1336 1477 1633 Actual Frequency 695.3 773.4 851.6 945.3 1210.9 1335.9 1476.6 1632.8 % Deviation -.20% +.40% -.05% +.46% +.20% .00% -.03% -.01%
COEFF 59h 63h 6Dh 79h 9Bh ABh BDh D1h
Table 2 - DTMF Frequencies
DTMF Signal to distortion: The sum of harmonic and noise power in the frequency band from 50 Hz to 3500 Hz is typically more than 30 dB below the power in the tone pair. All individual harmonics are typically more than 40 dB below the level of the low group tone.
Table 2 gives the standard DTMF frequencies, the coefficient required to generate the closest frequency, the actual frequency generated and the percent deviation of the generated tone from the nominal. Tone Ringer A dual frequency squarewave ringing signal may be applied to the handsfree speaker driver to generate a call alerting signal. To enable this mode the Ring En bit (address 18h) must be set as well as the ringer function to the loudspeaker via the Receive Path Control Register (address 13h). Ring En is independent of the DTMF enable control bits (see Lo EN and Hi EN). Since both functions use the same coefficient registers they are not usually enabled simultaneously. The digital tone generator uses the values programmed into the low and high Tone Coefficient Registers (addresses 1Ah and 1Bh) to generate two different squarewave frequencies. Both coefficients are determined by the following equation: COEFF = [32000/Frequency (Hz)] - 1 where COEFF is an integer between 1 and 255. This produces frequencies between 125 - 16000 Hz with a nonlinear resolution. The ringer program switches between these two frequencies at a 5 Hz or 10 Hz rate as selected by the WR bit in the DTMF/Tone ringer register (address 18h).
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Anti-Howl
Data Sheet
IDPC includes an Anti-Howling circuit plus speaker gain control circuit to allow for group listening operation. Although this is the main function of the circuit there are additional modes in which it may be used as defined by the MS1 and MS0 control bits (address 1Ch). MS1 0 0 1 1 MS0 0 1 0 1 Operational Mode Tx noise reduction (squelch) Rx noise reduction (squelch) switched loss group listening (anti-howling) Tx/Rx switched loss
The circuit is enabled by setting the Anti-howl Enable bit (address 1Ch) and selecting the required operational mode (MS0 & MS1) as described. For all modes of operation the switching levels and inserted loss are programmed as follows. Switching decisions are made by comparing either the transmit or the receive signal level to threshold levels stored in the High Threshold Register (address 1Dh) and the Low Threshold Register (address 1Eh). Threshold data is encoded in PCM sign-magnitude format excluding the sign bit. For example; THh0 - THh3 encode the PCM step number while THh4 - THh6 encode the PCM chord number for the high threshold. Similarly for the THl0 - THl6 bits of the low threshold. The difference between the high and low threshold levels provides the circuit with hysteresis to prevent uncontrolled operation. The low level threshold must never be programmed to a value higher than the one stored in the high level threshold. If this occurs the circuit will become unstable. Loss is implemented, in the chosen path, by subtracting the value set by the Pad0 - Pad3 control bits from the appropriate gain value set by the RxG0 - RxG3 or TxG0 - TxG3 control bits (see Digital Gain Register, address 19h). The minimum digital gain is limited to -24 dB regardless of the mathematical result of this operation. The path without loss reverts to the gain value programmed into the Digital Gain Register. The magnitude of the switched loss defaults to 12 dB on power up but can be programmed to between 0 and 21 dB using the Pad0 - Pad2 control bits (address 1Ch). Pad2 0 0 0 0 1 1 1 1 Pad1 0 0 1 1 0 0 1 1 Pad0 0 1 0 1 0 1 0 1 Attenuation (dB) 0 3 6 9 12 15 18 21
Switched Loss for Group Listening (anti-howling) Group listening is defined as a normal handset conversation with received speech also directed to the loudspeaker for third party observation. In this mode, if the handset microphone is moved into close proximity of the loudspeaker a feedback path will occur resulting in a singing connection. To prevent this the anti-howling circuit introduces a switched loss into either the transmit or receive paths dependent upon the transmit path speech activity. Loss switching is determined by comparing the signal level in the transmit path with the high level threshold stored at address 1Dh. When the transmit signal level exceeds this threshold the programmed loss is switched from the transmit path to the receive path. Once switching has occurred the transmit signal level is then compared to a low level threshold stored at address 1Eh. When the transmit signal level falls below this threshold the programmed loss is switched from the received path back to the transmit path and comparison reverts back to the high threshold level.
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Data Sheet
Since the received digital gain control is used to set the listening level of the received speech, for both handset receiver and loudspeaker, it is necessary to provide additional gain in the loudspeaker path so that its receive level can be controlled independently from the receiver output. The Gain0 to Gain3 control bits (address 0Bh) are used to boost the loudspeaker output to a comfortable listening level for the third parties in group listening. Generally the Gain3 bit should be set to logic 1 in this mode. This increases the gain programmed via the Gain0 - Gain2 bits by a factor of 8 dB. In group listening a speaker gain setting of 4 to 16 dB will be required to set a comfortable group listening level after the handset user has adjusted their listening level as required. Since the anti-howling circuit has dynamic control over the transmit and receive gain control registers, it is recommended that this function be turned off momentarily when DTMF tone generation is required. This will ensure that the proper transmit levels are attained. Transmit Noise Reduction (squelch) The transmit signal may be muted to eliminate transmission of excessive background noise. In this mode the signal level in the transmit path is compared with the high level threshold stored at address 1Dh. When the transmit signal level exceeds this threshold no loss is inserted into the transmit path. After exceeding the high level threshold the transmit signal level is then compared to a low level threshold stored at address 1Eh. When the transmit signal level falls below this threshold the transmit digital gain is reduced by the programmed amount (Pad0-2) and comparison reverts back to the high threshold level. The receive path gain is not altered by transmit noise reduction. Receive Noise Reduction (squelch) The receive signal may be muted to eliminate background noise resulting from a poor trunk connection. In this mode the signal level in the receive path is compared with the high level threshold stored at address 1Dh. When the receive signal level exceeds this threshold no loss is inserted into the receive path. After exceeding the high level threshold the receive signal level is then compared to a low level threshold stored at address 1Eh. When the receive signal level falls below this threshold the receive digital gain is reduced by the programmed amount (Pad2-0) and comparison reverts back to the high threshold level. The transmit path gain is not altered by receive noise reduction. Tx/Rx Switched Loss In this mode the programmed switched loss is inserted into either the transmit or receive path dependent only upon activity in the receive path. If receive path activity is above the programmed high level threshold then the switched loss is inserted into the transmit path. If receive path activity is below the programmed low level threshold then the switched loss is inserted into the receive path. This mode can be used to implement a loudspeaking function where the receive audio is routed to the SPKR pins and transmit audio is sourced from the MIC+ pin. In this mode there is no algorithmic cancellation of echo so it is recommended that this switched loss program be used only in 4-wire systems (i.e., digital set to digital set). Transducer Interfaces Four standard telephony transducer interfaces plus an auxiliary I/O are provided by the IDPC. These are: * The handset microphone inputs (transmitter), pins M+/M- and the answerback microphone input MIC+. The nominal transmit path gain may be adjusted to either 6.0 dB or 15.3 dB. Control of this gain is provided by the TxINC control bit (Control register 2, address 0Fh). This gain adjustment is in addition to the programmable gain provided by the transmit filter and Digital Gain circuit. The handset speaker outputs (receiver), pins HSPKR+/HSPKR-. This internally compensated, fully differential output driver is capable of driving the load shown in Figure 4. The nominal handset receive path gain may be adjusted to either -12.1 dB or -9.6 dB. Control of this gain is provided by the RxINC control bit (Control
*
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Data Sheet
register 2, address 0Fh). This gain adjustment is in addition to the programmable gain provided by the receive filter and Digital Gain circuit. * * The loudspeaker outputs, pins SPKR+/SPKR-. This internally compensated, fully differential output driver is capable of directly driving 6.5v p-p into a 40 ohm load. The Auxiliary Port provides an analog I/O, pins AUXin and AUXout, for connection of external equipment to the CODEC path as well as allowing access to the speaker driver circuits. * * * AUXin is a single ended high impedance input (>10 Kohm). This is a self-biased input with a maximum input range of 2.5vp-p. Signals should be capacitor-coupled to this input. AUXout is a buffered output capable of driving 40 Kohms//150 pF. Signals for this output are derived from the receive path or from the AUXin and transmit microphones. Auxiliary port path gains are: AUXin to Dout Din to AUXout AUXin to AUXout AUXin to HSPKR AUXin to SPKR 11 dB 20.3 dB -12 dB -7.0 dB -1.1 dB 1.4 dB 5.0 dB TxINC=0 TxINC=1
RxINC=0 RxINC=1
Refer to the application diagrams of Figures 10 and 11 for typical connections to this analog I/O section.
HSPKR +
75
IDPC
150 ohm load (speaker)
75
HSPKR -
Figure 4 - Handset Speaker Driver Microport The serial microport, compatible with Intel MCS-51 (mode 0), Motorola SPI (CPOL=0,CPHA=0) and National Semiconductor Microwire specifications provides access to all IDPC internal read and write registers. This microport consists of a transmit/receive data pin (DATA1), a receive data pin (DATA2), a chip select pin (CS) and a synchronous data clock pin (SCLK). The microport dynamically senses the state of the serial clock each time chip select becomes active. The device then automatically adjusts its internal timing and pin configuration to conform to Intel or Motorola/National requirements. If SCLK is high during chip select activation then Intel mode 0 timing is assumed. The DATA1 pin is defined as a bi-directional (transmit/receive) serial port and DATA2 is internally disconnected. If SCLK is low during chip select activation then Motorola/National timing is assumed. Motorola processor mode CPOL=0, CPHA=0 must be used. DATA1 is defined as the data transmit pin while DATA2 becomes the data receive pin. Although the dual
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Data Sheet
port Motorola controller configuration usually supports full-duplex communication, only half-duplex communication is possible in IDPC. The micro must discard non-valid data which it clocks in during a valid write transfer to IDPC. During a valid read transfer from IDPC data simultaneously clocked out by the micro is ignored by IDPC. All data transfers through the microport are two-byte transfers requiring the transmission of a Command/Address byte followed by the data byte written or read from the addressed register. CS must remain asserted for the duration of this two-byte transfer. As shown in Figures 5 and 6 the falling edge of CS indicates to the IDPC that a microport transfer is about to begin. The first 8 clock cycles of SCLK after the falling edge of CS are always used to receive the Command/Address byte from the microcontroller. The Command/Address byte contains information detailing whether the second byte transfer will be a read or a write operation and at what address. The next 8 clock cycles are used to transfer the data byte between the IDPC and the microcontroller. At the end of the two-byte transfer CS is brought high again to terminate the session. The rising edge of CS will tri-state the output driver of DATA1 which will remain tri-stated as long as CS is high. Intel processors utilize least significant bit first transmission while Motorola/National processors employ most significant bit first transmission. The IDPC microport automatically accommodates these two schemes for normal data bytes. However, to ensure timely decoding of the R/W and address information, the Command/Address byte is defined differently for Intel operation than it is for Motorola/National operation. Refer to the relative timing diagrams of Figures 5 and 6. Receive data is sampled on the rising edge of SCLK while transmit data is made available concurrent with the falling edge of SCLK. Detailed microport timing is shown in Figure 15.
COMMAND/ADDRESS
DATA INPUT/OUTPUT
COMMAND/ADDRESS:
DATA 1 RECEIVE D0 D1 D2 D3 D4 D5 D6 D7
D0 D1 D2 D3 D4 D5 D6 D7
D0 D1 D2 D3 D4 D5 D6 D7
DATA 1 TRANSMIT SCLK y
D0 D1 D2 D3 D4 D5 D6 D7
D0 D1 D2 D3 D4 D5 D6 D7
CS Delays due to internal processor timing which are transparent to IDPC.

y The IDPC:- latches received data on the rising edge of SCLK. - outputs transmit data on the falling edge of SCLK. The falling edge of CS indicates that a COMMAND/ADDRESS byte will be transmitted from the microprocessor. The subsequent byte is always data until terminated via CS returning high. A new COMMAND/ADDRESS byte may be loaded only by CS cycling high then low again. D7 The COMMAND/ADDRESS byte contains: 1 bit - Read/Write 5 bits - Addressing Data 2 bits - Unused X X A4 A3 A2 A1
D0 A0 R/W
Figure 5 - Serial Port Relative Timing for Intel Mode 0
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COMMAND/ADDRESS DATA INPUT/OUTPUT
Data Sheet
COMMAND/ADDRESS:
DATA 2 RECEIVE D7 D6 D5 D4 D3 D2 D1 D0
D7 D6 D5 D4 D3 D2 D1 D0
D7 D6 D5 D4 D3 D2 D1 D0
DATA 1 TRANSMIT SCLK y
D7 D6 D5 D4 D3 D2 D1 D0
D7 D6 D5 D4 D3 D2 D1 D0
CS Delays due to internal processor timing which are transparent to IDPC.

y The IDPC:- latches received data on the rising edge of SCLK. - outputs transmit data on the falling edge of SCLK. The falling edge of CS indicates that a COMMAND/ADDRESS byte will be transmitted from the microprocessor. The subsequent byte is always data until terminated via CS returning high. A new COMMAND/ADDRESS byte may be loaded only by CS cycling high then low again. D7 The COMMAND/ADDRESS byte contains: 1 bit - Read/Write 5 bits - Addressing Data 2 bits - Unused R/W X A4 A3 A2 A1
D0 A0 X
Figure 6 - Serial Port Relative Timing for Motorola Mode 00/National Microwire
125 s F0i
DSTi, DSTo
CHANNEL 0 D-channel LSB first for DChannel
CHANNEL 1 C-channel
CHANNEL 2 B1-channel
CHANNEL 3 B2-channel
CHANNELS 4-31 Not Used
MSB first for C, B1- & B2Channels
Figure 7 - ST-BUS Channel Assignment Flexible Digital Interface A serial link is required to transport data between the IDPC and an external digital transmission device. IDPC utilizes the ST-BUS architecture defined by Zarlink Semiconductor but also supports a strobed data interface found on many standard CODEC devices. This interface is commonly referred to as Synchronous Serial Interface (SSI). The combination of ST-BUS and SSI provides a Flexible Digital Interface (FDI) capable of supporting all Zarlink basic rate transmission devices as well as many other 2B + D transceivers. The required mode of operation is selected via the ST-BUS/SSI control bit (FDI Control Register, address 10h). Pin definitions alter dependent upon the operational mode selected, as described in the following subsections as well as in the Pin Description tables. Quiet Code The FDI can be made to send quiet code to the decoder and receive filter path by setting the RxMUTE bit high. Likewise, the FDI will send quiet code in the transmit (DSTo) path when the TxMUTE bit is high. Both of these
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
control bits reside in Control Register 1 at address 0Eh. When either of these bits are low their respective paths function normally. The -Zero entry of Table 1 is used for the quiet code definition. ST-BUS Mode The ST-BUS consists of output (DSTo) and input (DSTi) serial data streams, in FDI these are named Dout and Din respectively, a synchronous clock input signal CLOCKin (C4i), and a framing pulse input (F0i). These signals are direct connections to the corresponding pins of Zarlink basic rate devices. Note that in ST-BUS mode the XSTL2 pin is not used. The CSL1 and CSL0 bits, as described in the SSI Mode section, are also ignored since the data rate is fixed for ST-BUS operation. However, the Asynch/Synch bit must be set to logic "0" for ST-BUS operation. The data streams operate at 2048 kb/s and are Time Division Multiplexed into 32 identical channels of 64 kb/s bandwidth. A frame pulse (a 244 nSec low going pulse) is used to parse the continuous serial data streams into the 32 channel TDM frames. Each frame has a 125 Second period translating into an 8 kHz frame rate. A valid frame begins when F0i is logic low coincident with a falling edge of C4i. Refer to Figure 12 for detailed ST-BUS timing. C4i has a frequency (4096 kHz) which is twice the data rate. This clock is used to sample the data at the 3/4 bit-cell position on DSTi and to make data available on DSTo at the start of the bit-cell. C4i is also used to clock the IDPC internal functions (i.e., Filter/CODEC, Digital gain and tone generation) and to provide the channel timing requirements. The IDPC uses only the first four channels of the 32 channel frame. These channels are always defined, beginning with Channel 0 after the frame pulse, as shown in Figure 7 (ST-BUS channel assignments). The first two (D & C) Channels are enabled for use by the DEN and CEN bits respectively, (FDI Control Register, address 10h). ISDN basic rate service (2B+D) defines a 16kb/s signalling (D) Channel. IDPC supports transparent access to this signalling channel. ST-BUS basic rate transmission devices, which may not employ a microport, provide access to their internal control/status registers through the ST-BUS Control (C) Channel. IDPC supports microport access to this C-Channel. DEN - D-Channel In ST-BUS mode access to the D-Channel (transmit and receive) data is provided through an 8-bit read/write register (address 15h) D-Channel data is accumulated in, or transmitted from this register at the rate of 2 bits/frame for 16 kb/s operation (1 bit/frame for 8 kb/s operation). Since the ST-BUS is asynchronous, with respect to the microport, valid access to this register is controlled through the use of an interrupt (IRQ) output. D-Channel access is enabled via the (DEn) bit. DEn: When 1, ST-BUS D-channel data (1 or 2 bits/frame depending on the state of the D8 bit) is shifted into/out of the Dchannel (READ/WRITE) register. When 0, the receive D-channel data (READ) is still shifted into the proper register while the DSTo D-channel timeslot and IRQ outputs are tri-stated (default). D8: When 1, D-Channel data is shifted at the rate of 1 bit/frame (8 kb/s). When 0, D-Channel data is shifted at the rate of 2 bits/frame (16 kb/s default). 16 kb/s D-Channel operation is the default mode which allows the microprocessor access to a full byte of DChannel information every fourth ST-BUS frame. By arbitrarily assigning ST-BUS frame n as the reference frame, during which the microprocessor D-Channel read and write operations are performed, then: a. A microport read of address 15 hex will result in a byte of data being extracted which is composed of four di-bits (designated by roman numerals I,II,III,IV). These di-bits are composed of the two D-Channel bits received during each of frames n, n-1, n-2 and n-3. Referring to Fig. 8a: di-bit I is mapped from frame n3, di-bit II is mapped from frame n-2, di-bit III is mapped from frame n-1 and di-bit IV is mapped from frame n.
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
The D-Channel read register is not preset to any particular value on power-up (PWRST) or software reset (RST). b. A microport write to Address 15hex will result in a byte of data being loaded which is composed of four dibits (designated by roman numerals I, II, III, IV). These di-bits are destined for the two D-Channel bits transmitted during each of frames n+1, n+2, n+3, n+4. Referring to Fig.8a: di-bit I is mapped to frame n+1, di-bit II is mapped to frame n+2, di bit III is mapped to frame n+3 and di bit IV is mapped to frame n+4. If no new data is written to address 15hex, the current D-channel register contents will be continuously retransmitted. The D-Channel write register is preset to all ones on power-up (PWRST) or software reset (RST). An interrupt output is provided (IRQ) to synchronize microprocessor access to the D-Channel register during valid ST-BUS periods only. IRQ will occur every fourth (eighth in 8 kb/s mode) ST-BUS frame at the beginning of the third (second in 8 kb/s mode) ST-BUS bit cell period. The interrupt will be removed following a microprocessor Read or Write of Address 15 hex or upon encountering the following frames's FP input, whichever occurs first. To ensure DChannel data integrity, microport read/write access to Address 15 hex must occur before the following frame pulse. See Figure 8b for timing. 8 kb/s operation expands the interrupt to every eight frames and processes data one-bit-per-frame. D-Channel register data is mapped according to Figure 8c.
IRQ Microport Read/Write Access FP n-3 n-2 n-1 n n+1 n+2 n+3 n+4*
DSTo/ DSTi Di-bit Group Receive D0 D-Channel
I
II D1 D2 D3 No preset value
D4
III
IV D5 D6 D7 Di-bit Group Transmit D0 D-Channel
I
D1 D2
II
D3
D4
III
D5 D6
IV
D7
Power-up reset to 1111 1111
* note that frame n+4 is equivalent to frame n of the next cycle.
Figure 8a - D-Channel 16 kb/s Operation
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
FP
C4i
C2 tir =500 nsec max Rpullup= 10 k tif =500 nsec max IRQ 8 kb/s operation 16 kb/s operation Microport Read/Write Access
Reset coincident with Read/Write of Address 15 Hex or next FP, whichever occurs first
Din
D0
D1
Figure 8b - IRQ Timing Diagram
FP Microport Read/Write Access IRQ
n-7 n-6 n-5 n-4 n-3 n-2 n-1 n n+1 n+2 n+3 n+4 n+5 n+6 n+7 n+8
D-Channel Di-bit Group Receive D-Channel
I D0 II D1 III D2 IV D3 V D4 VI D5 VII D6 VIII D7 I D0 II D1 III D2 IV D3 V D4 VI D5 VII D6 VIII D7
No preset value
Di-bit Group Transmit D-Channel
Power-up reset to 1111 1111
Figure 8c - D-Channel 8 kb/s Operation CEn - C-Channel Channel 1 conveys the control/status information for the layer 1 transceiver. C-Channel data is transferred MSB first on the ST-BUS by IDPC. The full 64 kb/s bandwidth is available and is assigned according to which transceiver is being used. Consult the data sheet for the selected transceiver for its C-Channel bit definitions and order of bit transfer. When CEN is high, data written to the C-Channel register (address 14h) is transmitted, most significant bit first, on DSTo. On power-up reset (PWRST) or software reset (RST, address 0Fh) all C-Channel bits default to logic high. Receive C-Channel data (DSTi) is always routed to the read register regardless of this control bit's logic state. When low, data transmission is halted and this timeslot is tri-stated on DSTo. B1-Channel and B2-Channel Channels 2 and 3 are the B1 and B2 channels, respectively. B-channel PCM associated with the Digital Gain, Filter/CODEC and transducer audio paths is selected on an independent basis for the transmit and receive paths. For example, the transmit path may use the B1 channel while the receive path uses the B2 channel. Although not normally required, this flexibility is allowed.
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
For ST-BUS mode the configuration of bits 0 to 3, at address 12h, defines both the source of transmit audio and the B-Channel destination. The configuration of this register permits selection of only one transmit B-Channel at a time. If no valid transmit path has been selected, via the Transmit Path Selection Register, for a particular B-Channel then that timeslot output on DSTo is tri-stated. When a valid receive path has been selected, via the Receive Path Selection Register (address 13h), the active receive B-Channel is governed by the state of the B2/B1 control bit in Control register 1 (address 0Eh). Refer to the Path Selection section for detailed information. SSI Mode The SSI BUS consists of input and output serial data streams named Din and Dout respectively, a Clock input signal (CLOCKin), and a framing strobe input (STB). A 4.096 MHz master clock, at CLOCKin, is required for SSI operation if the bit clock is less than 512 kHz. The timing requirements for SSI are shown in Figures 13 and 14. In SSI mode the IDPC supports only B-Channel operation. The internal C and D Channel registers used in ST-BUS mode are not functional for SSI operation. The control bit B2/B1, as described in the ST-BUS section, is ignored since the B-Channel timeslot is defined by the input STB strobe. Hence, in SSI mode transmit and receive BChannel data are always in the channel defined by the STB input. The data strobe input STB determines the 8-bit timeslot used by the device for both transmit and receive data. This is an active high signal with an 8 kHz repetition rate. SSI operation is separated into two categories based upon the serial data rate. If the bit clock is 512 kHz or greater then the bit clock is used directly by the internal IDPC functions allowing synchronous operation. In this case, the bit clock is connected directly to the CLOCKin pin while XSTAL2 is left unconnected. If the available bit clock rate is 128 kHz or 256 kHz then a 4096 kHz master clock is required to derive clocks for the internal IDPC functions. If this clock is available externally then it may be applied directly to the CLOCKin pin. If a 4096 kHz clock is not available then provision is made to connect a 4096 kHz crystal across the CLOCKin and XSTAL2 pins as shown in Figure 9. The oscillator circuit has been designed to require an external feedback resistor and load capacitors. This configuration allows normal ST-BUS operation and synchronous SSI operation with clocks which are not loaded by these extra components.
CLOCKin 33 pF 100 k
XSTL2 33 pF 4096 kHz Nominal
Figure 9 - External Crystal Circuit (for asynchronous operation) Applications where the bit clock rate is below 512 kHz are designated as asynchronous. The IDPC will generate and re-align its internal clocks to allow operation when the external master and bit clocks are asynchronous. In this case, the external bit clock is not connected to the IDPC. Control bits Asynch/Synch, CSL1 and CSL0 in FDI Control Register (address 10h) are used to program the bit rates as shown in Table 3.
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Zarlink Semiconductor Inc.
MT9196
Asynch/ CSL1 CSL0 Synch 1 1 0 0 0 0 0 0 0 0 1 1 0 1 0 1 0 1 Table 3 Bit Clock Rate (kHz) 128 256 512 1536 2048 4096 CLOCKin (kHz) 4096 mandatory 4096 mandatory 512 1536 2048 4096
Data Sheet
For synchronous operation data is sampled, from Din, on the falling edge of the bit clock during the time slot defined by the STB input. Data is made available, on Dout, on the rising edge of the bit clock during the time slot defined by the STB input. Dout is tri-stated at all times when STB is not true. If STB is valid but no transmit path has been selected (via the Transmit Path Control Register) then quiet code will be transmitted on Dout during the valid strobe period. There is no frame delay through the FDI circuit for synchronous operation. For asynchronous operation Dout and Din are as defined for synchronous operation except that data is transferred according to the internally generated bit clock. Due to resynchronization circuitry activity, the output jitter on Dout is nominally larger but will not affect operation since the bit cell period at 128 kb/s and 256 kb/s is relatively large. There is a one frame delay through the FDI circuit for asynchronous operation. Refer to the specifications of Figures 13 and 14 for both synchronous and asynchronous SSI timing. Path Selection Transmit and receive audio paths are independently programmed through their respective Path Control Registers at addresses 12h and 13h. Individual audio path circuit blocks are powered up only as they are required to satisfy the programmed values in the path control registers. More detail is provided in the Power-up/down Reset section. Transmit Transmit audio path configuration (Path Control Register, address 12h) is simply a matter of assigning one of the three analog signal inputs, or the digital tone generator, to the required transmit B- Channel. Intermediate functions such as the transmit filter, encoder and transmit gain are automatically powered up and assigned as required. If transmit tones is selected then the digital tone generator must be programmed and enabled properly as described in the Digital Tone Generator section. Note that transmit tones may be enabled independently of the receive path. For ST-BUS mode the configuration of bits 0 to 3, at address 12h, defines both the source of transmit audio and the B-Channel destination. The configuration of this register permits selection of only one transmit B-Channel at a time. For SSI mode only the selections where bit 3 = 0 are allowed. This is because the B-Channel timeslot is defined by the input strobe at STB. If a selection where bit 3 = 1 is made it will be treated the same as the condition where B3 - B0 = all zero's. All reserved configurations should not be used. Receive The receive path assignment (Receive Path Control Register, address 13h) is different from the transmit path assignment. In this case a particular analog output port is assigned a source for its audio signal. The receive filter audio path and the Auxiliary In analog port are the available choices. This configuration allows flexibility in assignment. Two examples; the receive filter path can be assigned to the handset receiver, for a standard handset conversation, while permitting the loudspeaker to announce a message originating from the Auxiliary In port. Or
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
perhaps the receive filter is assigned to both the loudspeaker and the Auxiliary Out port. This would allow a voice recorder or Facsimile machine, connected to the AUXout port to be monitored over the loudspeaker. The receive filter path itself has two possible signal sources, PCM from the Din port or synthesized tones, from the digital tone generator. In both cases receive digital gain is assigned automatically. The Receive Path Control Register combines all of these choices into simple output port assignments. In ST-BUS mode receive PCM from the Din port must be selected from either the B1 or the B2 channel. Control Bit B2/B1 in Control Register 1 (address 0Eh) is used to define the active receive B-Channel. In SSI mode the active PCM channel is automatically defined by the STB input signal. Sidetone A voice sidetone path provides proportional transmit signal summing into the receive handset transducer driver. Details are provided in the Filter/CODEC section. Watchdog To maintain program integrity an on-chip watchdog timer is provided for connection to the microcontroller reset pin. The watchdog output WD goes high while the IDPC is held in reset via PWRST. Release of PWRST will cause WD to return low immediately and will also start the watchdog timer. The watchdog timer is clocked on the falling edge of STB/F0i and requires only this input, along with VDD, for operation. Note that in SSI mode, if STB disappears the watchdog will stop clocking. This will not harm processor operation but there is no longer any protection provided. If the watchdog reset word is written to the watchdog register (address 11h) after PWRST is released, but before the timeout period (T=512 mSec) expires, a reset of the timer results and WD will remain low. Thereafter, if the reset word is loaded correctly at intervals less than 'T' then WD will continue low. The first break from this routine, in which the watchdog register is not written to within the correct interval or it is written to with incorrect data, will result in a high going WD output after the current interval 'T' expires. WD will then toggle at this rate until the watchdog register is again written to correctly. 5-Bit Watchdog Reset Word B7 X B6 X B5 X B4 0 B3 1 B2 0 B1 1 B0 0
x=don't care
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Zarlink Semiconductor Inc.
MT9196
Power-up/down & PWRST/Software Reset
Data Sheet
While the IDPC is held in PWRST no device control or functionality is possible. While in software reset (RST=1, address 0Fh) only the microport and watchdog are functional. Software reset can only be removed by writing RST logic low or by the PWRST pin. After Power-up reset (PWRST) or software reset (RST) all control bits assume their default states; -Law functionality, usually 0 dB programmable gains and all sections of IDPC, except the microport and watchdog, into powered down states. This is the low power, stand-by condition. This includes: * The receive output drive transducers. All transducer output drivers are powered down forcing the output signals into tri-state. Output drivers (handset, handsfree-speaker, AUXout) are powered up/down individually as required by the state of the programmed bits in the Receive Path Control Register (address 13h) The transmit and receive filters and CODEC. All clocks for this circuit block are disabled. The complete section is automatically powered up as required by the programmed bits in the Transmit and Receive Path Control registers (addresses 12h and 13h). Whenever all path control selections are off this section is powered down. The CODEC and transmit/ receive filters cannot be powered up individually. The VRef and VBias circuits. Reference and Bias voltage drivers are tri-stated during power down causing the voltage at the pins to float. This circuit block is automatically powered up/down as it is required by either the Filter/CODEC or the transducer driver circuits. Whenever all path control selections are off this section is powered down. If the AUXin path to (any combination of the) output transducer drivers is selected then the VRef/VBias circuit is powered up but the Filter/CODEC circuit is not. The FDI and oscillator circuits. After PWRST, the device assumes SSI operation with Dout tri-stated while there is no strobe active on STB. If a valid strobe is supplied to STB, then Dout will be active, during the defined channel, supplying quiet code as defined in Table 1. If the device is switched to ST-BUS operation following PWRST, the entire Dout stream will be tri-stated until an active transmit channel is programmed. As well, following PWRST, the oscillator circuit is disabled and all timing for the IDPC functional blocks is halted. A clock signal applied to the MCL pin is prevented from entering further into the IDPC when the Asynch/Synch bit is logic "1".
*
*
*
To power up the FDI and oscillator circuits the PD bit of Control Register 1 (address 0Eh) must be cleared. To attain complete power-down from a normal operating condition, write all "0s" to the Transmit and Receive Path Control Registers (address 12h and 13h), set PD to logic 1 at address 0Eh, and Asynch/Synch to logic 1 at address 10h.
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Zarlink Semiconductor Inc.
MT9196
IDPC Register Map
00 * * * 09 0A 0B 0C 0D 0E 0F Gain3 RxFG2 Gain2 RxFG1 Gain1 RxFG0 Gain0 -
Data Sheet
RESERVED
TxFG2 STG2
TxFG1 STG1
TxFG0 STG0
FCodec Control 1 FCodec Control 2
---------------------------------------RESERVED------------------------------------------------------------------------RESERVED---------------------------------PD RST Tfhp DialEn A/ Smag/ CCITT DEN W4 b4 b4 D4 RxINC B2/B1 TxINC RxMute TxMute Control Register 1 Control Register 2
10 11 12 13 14 15 16 17 18 19 1A 1B 1C 1D 1E 1F * * * 3F
b7 b7 D7
ST-BUS/ SSI b6 b6 D6
CEN b5 b5 D5
D8 W3 b3 b3 b3 D3
Asynch/ Synch W2 b2 b2 b2 D2
CSL1 W1 b1 b1 b1 D1
CSL0 W0 b0 b0 b0 D0
FDI Control Watchdog Tx Path Control Rx Path Control C-Channel Register D-Channel Register
---------------------------------------RESERVED---------------------------------HiEN TxG3 L7 H7 Enable LoEn TxG2 L6 H6 THh6 THl6 Loop2 DTMF StEn TxG1 L5 H5 MS1 THh5 THl5 Loop1 Ring En TxG0 L4 H4 MS0 THh4 THl4 RxG3 L3 H3 THh3 THl3 RxG2 L2 H2 Pad2 THh2 THl2 RxG1 L1 H1 Pad1 THh1 THl1 WR RxG0 L0 H0 Pad0 THh0 THl0 Loopback Register DTMF/Tone Ringer Digital Gain Low Tone Coeff High Tone Coeff Anti-Howl Control High Threshold Low Threshold
RESERVED
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Zarlink Semiconductor Inc.
MT9196
Register Summary
Data Sheet
ADDRESSES = 00h to 09h ARE RESERVED Filter Codec Control Register 1 7
RxFG2 RxFG1 RxFG0
-
ADDRESS = 0Ah WRITE/READ VERIFY
TxFG2 TxFG1 TxFG0
Power Reset Value X000 X000
6
5
4
3
2
1
0
Receive Gain Setting (dB)
(default)
RxFG2 0 0 0 0 1 1 1 1
RxFG1 0 0 1 1 0 0 1 1
RxFG 0 0 1 0 1 0 1 0 1
Transmit Gain Setting (dB) (default) 0 1 2 3 4 5 6 7
TxFG2 0 0 0 0 1 1 1 1
TxFG1 0 0 1 1 0 0 1 1
TxFG0 0 1 0 1 0 1 0 1
0
-1 -2 -3 -4 -5 -6 -7
RxFGn = Receive Filter Gain n
TxFGn = Transmit Filter Gain n
Filter Codec Control Register 2
Gain3 Gain2 Gain1 Gain0
-
ADDRESS = 0Bh WRITE/READ VERIFY
STG2 STG1 STG0
Power Reset Value 0010 X000
7
6
5
4
3
2
1
0
Speaker Gain (dB) Gain3 = 1 16 12 8 4 0 -4 -8 -12 Gain3 = 0 8 4 0 -4 -8 -12 -16 -20
Gain2 0 0 0 0 1 1 1 1
Gain1 0 0 1 1 0 0 1 1
Gain0 0 1 0 1 0 1 0 1
Side-tone Gain Setting (dB) (default) OFF -9.96 -6.64 -3.32 0 3.32 6.64 9.96
STG2 0 0 0 0 1 1 1 1
STG1 0 0 1 1 0 0 1 1
STG 0 0 1 0 1 0 1 0 1
STGn = Side-tone Gain n
ADDRESS = 0Ch RESERVED
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
ADDRESS = 0Dh RESERVED
Control Register 1
PD Tfhp DialEN
ADDRESS = 0Eh WRITE/READ VERIFY 4
-
B2/B1 RxMute TxMute
Power Reset Value 100X X000
7
PD Tfhp DialEN B2/B1 RxMUTE TxMUTE
6
5
3
2
1
0
When high, the crystal oscillator and FDI blocks are powered down. When low, the oscillator and FDI circuits are active. When High, an additional highpass function (passband beginning at 400 Hz) is inserted into the transmit path. When low, this highpass filter is disabled. When high, a first order lowpass filter is inserted into the receive path (3 dB = 1.2 kHz). When low, this lowpass filter is disabled. When high, the receive Filter/CODEC operates on the B2-Channel. When low, the receive Filter/CODEC operates on the B1-Channel. This control bit has significance only for ST-BUS operation and is ignored for SSI operation. When high the received PCM stream is interrupted and replaced with quiet code; thus forcing the receive path into a mute state. When low the full receive path functions normally. When high the transmit PCM stream is interrupted and replaced with quiet code; thus forcing the output code into a mute state (only the output code is muted, the transmit microphone and transmit Filter/CODEC are still functional). When low the full transmit path functions normally.
Control Register 2
RST
ADDRESS = 0Fh WRITE/READ VERIFY 6
A/ Smag/ CCITT RxINC TxINC
1
0
Power Reset Value 0X00 00XX
7
RST
5
4
3
2
A/ Smag/CCITT
RxINC TxINC
When high, a software reset occurs performing the same function as the hardware reset (PWRST) except that the microport and watchdog circuitry are not affected. A software reset can be removed only by writing this bit low or by a PWRST. When low, the reset condition is removed. When high, A-Law (de)coding is selected for the Filter/CODEC and DTMF generator circuits. When low, -Law (de)coding is selected for these circuits. When high, sign-magnitude code assignment is selected for the CODEC input/output. When low, CCITT code assignment is selected for the CODEC input/output; true sign, inverted magnitude (-Law) or true sign, alternate digit inversion (A-Law). When high, the receiver driver nominal gain is set at -9.6 dB. When low, this driver nominal gain is set at -12.1 dB. When high, the transmit amplifier nominal gain is set at 15.3 dB. When low, this amplifier nominal gain is set at 6.0 dB.
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
FDI Control Register 7
ST-BUS/SSI CEN ST-BUS/ CEN SSI
Data Sheet
ADDRESS = 10h WRITE/READ VERIFY
DEN
D8
Asynch/ Synch
CSL1
CSL0
Power Reset Value X000 0000
6
5
4
3
2
1
0
DEN
D8 Asynch/Synch, CSL1,CSL0
When high, the FDI port operates in ST-BUS mode. When low, the FDI operates in SSI mode. When high, data written into the C-Channel register (address 14h) are transmitted during channel 1 on DSTo. When low, the channel 1 timeslot is tri-stated on DSTo. Channel 1 data received on DSTi is read via the CChannel register (address 14h) regardless of the state of CEN. This control bit has significance only for ST-BUS operation and is ignored for SSI operation. When high, data written into the D-Channel Register (address 15h) are transmitted during channel 0 on DSTo. When low, the channel 0 timeslot is tri-stated on DSTo. Channel 0 data received on DSTi is read via the DChannel register regardless of the state of DEN. This control bit has significance only for ST-BUS mode and is ignored for SSI operation. When high, the D-Channel operates at 8 kb/s. When low, the D-Channel operates at 16 kb/s default. Control bits Asynch/Synch, CSL1 and CSL0 are used to program the data clock (BCL) bit rates as shown in the following table (CSL1 and CSL0 are ignored in ST-BUS mode): CSL1 0 0 0 0 1 1 CSL0 0 1 0 1 0 1 Bit Clock Rate (kHz) 128 256 512 1536 2048 4096 CLOCKin (kHz) 4096 mandatory 4096 mandatory 512 1536 2048 4096
Asynch/Synch 1 1 0 0 0 0
Note: Asynch/Synch must be set low for ST-BUS operation
Watchdog Register 7 6 5 0 4
1
ADDRESS = 11h WRITE 0 2 1 1 0 0
Power Reset Value XXXX XXXX
3
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
Transmit Path Control Register 7 6 5 4
b3 b2 b1
Data Sheet
ADDRESS = 12h WRITE/READ VERIFY
b0
Power Reset Value XXXX 0000
3
2
1
0
Control bits b0 to b3 are used to configure the transmit path and select the transmit source. Note that for SSI mode all selections where b3 = 1 are not used and are interpreted as b0 - b3 = 0 (i.e., transmit path off).
Destination B1
Source Programming b3 0 0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 b2 0 0 0 0 1 1 1 1 0 0 0 0 1 1 1 1 b1 0 0 1 1 0 0 1 1 0 0 1 1 0 0 1 1 b0 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1 B1 & B2 Off Handset mic (M + /M -) Handsfree mic (MIC +) AUXin Tx tones Reserved Reserved Reserved Reserved Handset mic (M + /M -) Handsfree ic (MIC +) AUXin Tx Tones Reserved Reserved Reserved
B2
Receive Path Control Register
b7 b6 b5 b4 b3 b2 b1
ADDRESS = 13h WRITE/READ VERIFY
b0
Power Reset Value 0000 0000
7
6
5
4
3
2
1
0
Control bits b0 to b7 are used to assign a signal source individually to each receive path output. In addition transmit to receive voice sidetone path control is included. Destination Handset Speaker b1 0 0 1 1 b3 0 0 1 1 b6 0 0 0 0 1 1 1 1 b7 0 1 b0 0 1 0 1 b2 0 1 0 1 b5 0 0 1 1 0 0 1 1 b4 0 1 0 1 0 1 0 1 Source Programming Off Rx Filter AUXin Reserved
Handsfree Speaker
Off Rx Filter AUXin Ringer
Aux out
Off Rx Filter Reserved AUXin Handset mic (M+ /M -) Handsfree mic (MIC +) Reserved Reserved
Voice Sidetone
Voice sidetone path disabled Voice sidetone path enabled
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
C-Channel Register
B7 B6 B5 B4 B3 B2 B1 B0
Data Sheet
ADDRESS = 14h WRITE/READ
Power Reset Value 1111 1111
7
6
5
4
3
2
1
0
Micro-port access to the ST-BUS C-Channel information
D-Channel Register
D7 D6 D5 D4 D3 D2 D1 D0
ADDRESS = 15h WRITE/READ
Power Reset Value 1111 1111
7
6
5
4
3
2
1
0
ADDRESS = 16h RESERVED
Loopback Register 7
Loop1
ADDRESS = 17h WRITE/READ VERIFY 6
Loop2 Loop1
-
2
1
0
Power Reset Value XX00 XXXX
5
4
3
Loop2
Notes:
When high, the selected B-channel in ST-BUS mode (i.e., B2/B1 and Transmit and Receive Path selections) or the strobed B-channel in SSI mode is looped back from Din to Dout through the FDI block. The C & D channels (ST-BUS mode) are not looped back. When low, the device operates normally. When high, Loop1 is invoked with the transmit and receive digital gain adjustment being included. This loopback should only be used if PCM resides in the B-channel. If a data pattern is being looped back then use Loop1 or use Loop2 after ensuring that the transmit and receive digital gain registers are set to 0dB (address 19h). When low, the device operates normally. 1) do not enable Loop1 and Loop2 simultaneously. 2) both loopback modes add an extra frame delay to the data transmission. 3) ensure that all other bits of address 17h are written logic low when accessing this register.
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
DTMF/Tone Ringer Control Register
HiEN
Data Sheet
ADDRESS = 18h WRITE/READ VERIFY
LoEN DTMF St EN 6 5
Ring En
-
2
1
WR
Power Reset Value 0000 XXX0
7
HiEN, LoEN DTMF St EN Ring EN
4
3
0
WR
When high, the programmed tone, for the respective high or low group, is generated. When low, tone generation is disabled for the respective low or high group. When high, programmed DTMF is muxed into the receive path replacing the receive PCM signal. When low, the receive path functions normally. When high, the tone ringer generator is enabled using the coefficients at addresses 1Ah and 1Bh as well as the WR control bit. For the ringer tone to be applied to the loudspeaker the proper path must be selected via the Receive Path Control Register (address 13h). When low, the ring generator circuit is disabled. When high, the tone ringer circuit will toggle between the two programmed frequencies at a 5 Hz rate. When low, the tone ringer warble rate is 10Hz.
Digital Gain Register
TxG3 TxG2 TxG1 TxG0 RxG3 RxG2 RxG1
ADDRESS = 19h WRITE/READ VERIFY
RxG0
Power Reset Value 1000 1000
7
6
5
4
3
2
1
0
Transmit (TxG3-0) and receive (RxG3-0) control bits for programming gain in 3 dB increments. RxG3 0 0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 RxG 2 0 0 0 0 1 1 1 1 0 0 0 0 1 1 1 1 RxG1 0 0 1 1 0 0 1 1 0 0 1 1 0 0 1 1 RxG0 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1 Gain Adjustment (dB) -24 -21 -18 -15 -12 -9 -6 -3 0 +3 +6 +9 +12 +15 +18 +21 TxG 3 0 0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 TxG2 0 0 0 0 1 1 1 1 0 0 0 0 1 1 1 1 TxG1 0 0 1 1 0 0 1 1 0 0 1 1 0 0 1 1 TxG0 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1
Low Tone Coefficient Register
L7 L6 L5 L4 L3 L2 L1
ADDRESS = 1Ah WRITE/READ VERIFY
L0
Power Reset Value 0000 0000
7
6
5
4
3
2
1
0
The frequency of the low group tone is programmed by writing an 8-bit hexadecimal coefficient at this address according to the following equation: Frequency (in Hz) = 7.8125 x COEFF Where the hexadecimal COEFF is converted into a decimal integer between 0 and 255. Frequency resolution is 7.8125Hz in the range 0 to 1992 Hz.
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
High Tone Coefficient Register
H7 H6 H5 H4 H3 H2 H1
Data Sheet
ADDRESS = 1Bh WRITE/READ VERIFY H0 0
Power Reset Value 0000 0000
7
6
5
4
3
2
1
The frequency of the high group tone is programmed by writing an 8-bit hexadecimal coefficient at this address according to the following equation: Frequency (in Hz) = 7.8125 x COEFF Where the hexadecimal COEFF is converted into a decimal integer between 0 and 255. Frequency resolution is 7.8125Hz in the range 0 to 1992 Hz.
Anti-Howl Control Register
Enable
ADDRESS = 1Ch WRITE/READ VERIFY
MS0
-
6
MS1
Pad2
Pad1
Pad0
Power Reset Value 0X10 X100
7
Enable MS1, MS0
5
4
3
2
1
0
Pad2-0
When high, the anti-howling circuit is enabled. When low, the anti-howling circuit is disabled. Encode the operational mode of the anti-howling circuit as follows. Details of each mode are found in the functional description of the anti-howling circuit. MS1 MS0 Operational Mode 0 0 Transmit Noise Squelch 0 1 Receive Noise Squelch 1 0 Anti-howling for group listening 1 1 Tx/Rx Switched Loss Three bits encoding the attenuation depth which will be switched into the transmit or receive paths by the anti-howling circuit. Note that 12 dB is the default value. Pad2 Pad1 Pad0 Attenuation (dB) 0 0 0 0 0 0 1 3 0 1 0 6 0 1 1 9 1 0 0 12 1 0 1 15 1 1 0 18 1 1 1 21
High Threshold Register 7
THh6-0
ADDRESS = 1Dh WRITE/READ VERIFY
THh5 THh4 THh3 THh2 THh1 THh0
Power Reset Value X011 0000
THh6
6
5
4
3
2
1
0
Seven bits encoding the magnitude of the high threshold level. Encoding is in PCM sign-magnitude excluding the sign bit. THh0 - THh3 encode the step number while THh4 - THh6 encode the chord number. The default setting of 'X011 0000' encodes chord 3 step 0. The difference between the high and low thresholds defines the hysteresis for anti-howling.
Low Threshold Register 7
THl6-0
ADDRESS = 1Eh WRITE/READ VERIFY
THI5 THI4 THI3 THI2 THI1 THI0
Power Reset Value X001 0100
THI6
6
5
4
3
2
1
0
Seven bits encoding the magnitude of the low threshold level. Encoding is in PCM sign-magnitude excluding the sign bit. THl0 - THl3 encode the step number while THl4 - THl6 encode the chord number. The default setting of 'X001 0100' encodes chord 1 step 4. The difference between the high and low thresholds defines the hysteresis for anti-howling.
ADDRESSES 1Fh to 3Fh are RESERVED
Note: Bits marked "-" are reserved bits and should be written with logic "0".
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Zarlink Semiconductor Inc.
MT9196
Applications
Data Sheet
330 + Typical External Gain for Handset AV= 5 - 10 Typical External Gain for MIC AV= 20 - 25 R Av = 1 + 2R T R + + 0.1 F VBias R VBias T 330 +5V 0.1 F 1K + 10F Electret + Microphone 0.1 F 4 +5V 5 6 7 CS INTEL MCS-51 or MOTOROLA SPI MicroController RESET SCLK DATA1 DATA2 8 9 10 11 3 2 1 28 27 26 From Auxiliary Audio Source 25 24 23 40 nom. 34 min. 75 0.1F To Auxiliary Audio Source T 100K 0.1 F VBias 100K 511 +5V + 10 F Electret + Microphone
0.1 F
511
IDPC
22 21 20 19 150 +5V 75
DATA2 Motorola Mode only WD IRQ DC to DC CONVERTER +5V DSTo DSTi F0 Lin ZT MT8972 DNIC C4 12 13 14 15 16 17 18
Twisted Pair Lout
10.24 MHz
Figure 10 - ST-BUS Application Circuit with MT8972 (DNIC)
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
330 + Typical External Gain for Handset AV= 5 - 10 Typical External Gain for MIC AV= 20 - 25 R Av = 1 + 2R T R + + 0.1 F VBias R VBias T 330 +5V 0.1 F 1K + 10F Electret + Microphone 0.1 F 4 +5V 5 6 7 CS INTEL MCS-51 or MOTOROLA SPI MicroController RESET SCLK DATA1 8 9 10 3 2 1 28 27 26 From Auxiliary Audio Source 25 24 23 40 nom. 34 min. 75 0.1F To Auxiliary Audio Source T 100K 0.1 F VBias 100K 511 +5V + 10 F Electret + Microphone
0.1 F
511
IDPC
22 21 20 19 150 +5V 75
11 DATA2 DATA2 Motorola Mode only WD IRQ 12 13 14 15 16 17 18
Twisted Pair
Layer 1 Transceiver using SSI Synch Mode
DOUT DIN BCL STB
DOUT DIN BCL STB
Layer 1 Transceiver using SSI Asynch Mode
Twisted Pair
4096 kHz Crystal 4096 kHz 4096 kHz External Clock from Layer 1 Device or other source
Figure 11 - SSI Application Circuit showing Synchronous or Asynchronous Operation
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Zarlink Semiconductor Inc.
MT9196
Programming Examples
Data Sheet
Some examples of the programming steps required to set-up various telephony functions are given. Note that these steps are from the power-up reset default definition. If some other state is currently true then some programming steps may be omitted while new ones may be required. Initialization Description choose ST-BUS vs SSI (ie ST-BUS with C&D channels enabled) or (ie SSI at 256kHz BCL) power up oscillator and FDI same as above with B2 channel for ST-BUS A-Law vs -Law as required (ie CCITT -Law and gains low) or (ie CCITT A-Law and gains increased) Standard Full-duplex handset call Description program Initialization steps above set sidetone gain (ie 0 dB) set gain (ie Rx = +3 dB, Tx = 0 dB) select transmit path (ie handset mic to B2 for ST-BUS) or (ie handset mic for SSI) select receive path (ie handset speaker to Rx filter plus sidetone) or (as above plus receive to AUXout also) optional: set Filter/CODEC Rx and Tx gain Group Listening Description program Initialization steps above set gain (ie Rx = +3 dB, Tx = 0 dB) set sidetone gain (ie 0 dB) and also set handsfree speaker gain independent of the rest of the receive path (ie 12dB) set high threshold level set low threshold level enable group listening with 12dB of atten. select transmit path (ie handset mic to B2 for ST-BUS) or (ie handset mic for SSI) select receive path (ie Rx filter to both handset and handsfree speakers with sidetone) 19h 0Bh 89h (or as required, defaults = 0dB) 94h Address DATA 0Bh 19h 12h 12h 13h 13h 04h (leave speaker gain defaulted to 0dB) 89h (or as required, defaults = 0dB) 09h 01h 81h (for standard headset only) 91h Address DATA Address 10h 10h 0Eh 0Eh 0Fh 0Fh DATA 70h 05h 00h (other bits as required) 04h (other bits as required) 00h (default value so no write required) 2Ch
0Ah
as required (0dB default)
1Dh 1Eh 1Ch 12h 12h 13h
as required or leave default value as required or leave default value A4h 09h 01h 85h
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Zarlink Semiconductor Inc.
MT9196
Generate tone ringer Description Address DATA Program Initialization steps above except A-Law vs -Law choices are not required. set speaker gain (ie -12dB) 0Bh 50h (or as required) write low tone coefficient 1Ah as required write high tone coefficient 1Bh as required select ringer as source for loudspeaker 13h 0Ch start tone ringer (warble = 5Hz) 18h 11h or (warble = 10Hz) 18h 10h (default) control ringer cadence by toggling 18h 10h (on) Ring EN (ie warble = 10Hz) 00h (off) 10h (on) 00h (off) etc... Generate DTMF tones transmit only Description Address DATA Program Initialization steps above set Tx digital gain (ie 0 dB) 19h 80h (or as required) (-4dBm0/-Law,-10dBm0/A-Law) write low tone coefficient 1Ah as required write high tone coefficient 1Bh as required select transmit path (ie Tx tones to B2 for ST-BUS) 12h 0Ch or (ie Tx tones for SSI) 12h 04h start DTMF 18h C0h (both Hi EN and Lo EN) or for single tones 18h 80h or 40h as required DTMF sidetones only Description Program Initialization steps above set Rx digital gain (ie 0 dB) (-28dBm0) write low tone coefficient write high tone coefficient select receive path (ie Rx Filter to handset) or (ie Rx Filter to handsfree speaker) or (ie Rx Filter to AUX out) start DTMF program with sidetone or for single tones DTMF transmit and sidetone Description Program Initialization steps above set Tx digital gain (ie 0 dB) (-4dBm0/-Law,-10dBm0/A-Law) set Rx digital gain (ie 0 dB) (-28dBm0) write low tone coefficient write high tone coefficient select transmit path (ie Tx tones to B2 for ST-BUS) or (ie Tx tones for SSI) select receive path (ie Rx Filter to handset) or (ie Rx Filter to handsfree speaker) or (ie Rx Filter to AUX out) start DTMF program with sidetone or for single tones
Data Sheet
Address 19h 1Ah 1Bh 13h 13h 13h 18h 18h
DATA 08h (or as required) as required as required 01h 04h 10h E0h (both Hi EN and Lo EN) A0h or 60h as required
Address 19h
DATA 88h (or as required)
1Ah 1Bh 12h 12h 13h 13h 13h 18h 18h
as required as required 0Ch 04h 01h 04h 10h E0h (both Hi EN and LO EN) A0h or 60h as required
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Zarlink Semiconductor Inc.
MT9196
Absolute Maximum Ratings Parameter 1 2 3 4 5 Supply Voltage Voltage on any I/O pin Current on any I/O pin (transducers excluded) Storage Temperature Power Dissipation (package) Plastic Symbol VDD - VSS VI/VO II/IO TS PD - 65 Min. - 0.3 VSS - 0.3 Max. 7
Data Sheet
Units V V mA C mW
VDD + 0.3 20 + 150 750
Recommended Operating Conditions - Voltages are with respect to VSS unless otherwise stated Characteristics 1 2 3 4 5 6 Supply Voltage TTL Input Voltage (high)* TTL Input Voltage (low)* CMOS Input Voltage (high) CMOS Input Voltage (low) Operating Temperature Sym. VDD VIHT VILT VIHC VILC TA Min. 4.75 2.4 VSS 4.5 VSS - 40 Typ. 5 Max. 5.25 VDD 0.4 VDD 0.5 + 85 Units V V V V V C Includes Noise margin = 400 mV Includes Noise margin = 400 mV Test Conditions
* Excluding PWRST which is a Schmitt Trigger Input.
Power Characteristics Characteristics 1 2 Supply Current (clock disabled, all functions off, PD=1) Supply Current by function: Filter/Codec Digital Gain/Tone Handset Driver (bias only, no signal) Speaker Driver (bias only, no signal) Timing Control, C-channel, ST-BUS, etc. Total all functions enabled Sym. IDDC1 Min. Typ. 400 Max. Units A Test Conditions Outputs unloaded, Input signals static, not loaded
IDDF1 IDDF2 IDDF3 IDDF4 IDDF5 IDDFT
1.5 1.5 1.25 1.25 1.0 14.0 19.0
mA mA mA mA mA mA
See Note 1. See Note 1.
See Notes 1 & 2.
Note 1: Power delivered to the load is in addition to the bias current requirements. Note 2: IDDFT is not additive to IDDC1 .
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Zarlink Semiconductor Inc.
MT9196
DC Electrical Characteristics - Voltages are with respect to ground (VSS) unless otherwise stated. Characteristics 1 2 3 4 5 6 7 Input HIGH Voltage TTL inputs Input LOW Voltage TTL inputs Input HIGH Voltage CMOS inputs Input LOW Voltage CMOS inputs VBias Voltage Output Input Leakage Current Positive Going Threshold Voltage (PWRST only) Negative Going Threshold Voltage (PWRST only) Output HIGH Current Output LOW Current Output Reference Voltage Output Leakage Current Output Capacitance Input Capacitance Sym. VIHT VILT VIHC VILC VBias IIZ VT+ VTIOH IOL VRef IOZ Co Ci -5 5 - 16 10
VDD/2-1.5
Data Sheet
Min. 2.0
Typ.
Max.
Units V
Test Conditions
0.8 3.5 1.5 VDD/2 0.1 3.7 1.3 10
V V V V A V V mA mA V A pF pF VOH = 2.4V VOL = 0.4V No load VOUT = VDD and VSS Max. Load = 10k VIN=VDD to VSS
8 9 10 11 12 13
0.01 15 10
10
DC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing.
CLOCKin Tolerance Characteristics Characteristics 1 CLOCKin (C4i) Frequency Min. 4095.6 Typ. 4096 Max. 4096.4 Units kHz Test Conditions
AC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing.
Preferred Crystal Characteristics Nominal Frequency Frequency Tolerance Operating Temperature Shunt Capacitance Drive Level Series Resistance Load Capacitance Frequency Stability 4096 kHz 100 ppm @25C -40C to +85C 7pF Maximum 5 mW 130 maximum 20 pF 0.003%/C from 25C
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Zarlink Semiconductor Inc.
MT9196
AC Characteristics for A/D (Transmit) Path - 0dBm0 = 1.421Vrms for -Law and 1.477Vrms for
A-Law, at the CODEC. (VRef=1.0 volts and VBias=2.5 volts.)
Data Sheet
Characteristics 1 Analog input equivalent to overload decision Absolute half-channel gain M to PCM
Sym. ALi3.17 ALi3.14
Min.
Typ. 5.79 6.0
Max.
Units Vp-p Vp-p
Test Conditions -Law A-Law Both at CODEC Transmit filter gain=0dB setting. Digital gain=0dB setting. TxINC = 0* TxINC = 1* TxINC = 0* TxINC = 1* TxINC = 0* TxINC = 1* @1020 Hz
2
GAX1 GAX2 GAX3 GAX4 GAX5 GAX6
5.0 14.3 9.5 18.8 9.5 18.8 -0.2
6.0 15.3 11 20.3 11 20.3
7.0 16.3 12.5 21.8 12.5 21.8 +0.2
dB dB dB dB dB dB dB
MIC + to PCM
AUXin to PCM
Tolerance at all other transmit filter settings (1 to 7dB) 3 Gain tracking vs. input level CCITT G.714 Method 2 Signal to total Distortion vs. input level CCITT G.714 Method 2 Transmit Idle Channel Noise Gain relative to gain at 1020Hz <50Hz 60Hz 200Hz 300 - 3000 Hz 3000 - 3400 Hz 4000 Hz >4600 Hz Absolute Delay Group Delay relative to DAX GTX
-0.3 -0.6 -1.6 35 29 24 15 -71
0.3 0.6 1.6
dB dB dB dB dB dB
3 to -40 dBm0 -40 to -50 dBm0 -50 to -55 dBm0 0 to -30 dBm0 -40 dBm0 -45 dBm0 -Law A-Law
4
DQX
5 6
NCX NPX GRX
16.5 -69 -25 -30 0.0 0.25 0.25 -12.5 -25
dBrnC0 dBm0p dB dB dB dB dB dB dB s s s s s
-0.25 -0.9
7 8
DAX DDX
360 750 380 130 750
at frequency of minimum delay 500-600 Hz 600 - 1000 Hz 1000 - 2600 Hz 2600 - 2800 Hz 100mVRMS VDD -law PSSR1-3 not production tested
9
Power Supply Rejection f=1020 Hz f=0.3 to 3 kHz f=3 to 4 kHz f=4 to 50 kHz PSSR PSSR1 PSSR2 PSSR3 37 40 35 40 dB dB dB dB
AC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25C and are for design aid only: not guaranteed and not subject to production testing. * Note: TxINC, refer to Control Register 2, address 0Fh.
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Zarlink Semiconductor Inc.
MT9196
Data Sheet
AC Characteristics for D/A (Receive) Path - 0dBm0 = 1.421Vrms for -Law and 1.477Vrms for A-Law, at the CODEC. (VRef=1.0
volts and VBias=2.5 volts.)
Characteristics 1 2 Analog output at the CODEC full scale Absolute half-channel gain
Sym. ALo3.17 ALo3.14
Min.
Typ. 5.704 5.906
Max.
Units Vp-p Vp-p
Test Conditions -Law A-Law Receive filter gain = 0dB setting. Digital gain = 0dB setting. RxINC = 0* RxINC = 1*
PCM to HSPKR PCM to SPKR PCM to AUXout Tolerance at all other receive filter settings (-1 to -7dB) 3 Gain tracking vs. input level CCITT G.714 Method 2 Signal to total distortion vs. input level CCITT G.714 Method 2 Receive Idle Channel Noise Gain relative to gain at 1020Hz 200Hz 300 - 3000 Hz 3000 - 3400 Hz 4000 Hz >4600 Hz Absolute Delay Group Delay relative to DAR
GAR1 GAR2 GAR3 GAR4
-13.1 -10.6 -1.0 -14 -0.2
-12.1 -9.6 0 -12
-11.1 -8.6 1.0 -10 +0.2 0.3 0.6 1.6
dB dB dB dB dB dB dB dB dB dB dB
@1020 Hz
GTR
-0.3 -0.6 -1.6 35 29 24 13 -78.5
3 to -40 dBm0 -40 to -50 dBm0 -50 to -55 dBm0 0 to -30 dBm0 -40 dBm0 -45 dBm0 -Law A-Law
4
GQR
5 6
NCR NPR GRR -0.25 -0.90
15.5 -77 0.25 0.25 0.25 -12.5 -25
dBrnC0 dBm0p dB dB dB dB dB s s s s s
7 8
DAR DDR
240 750 380 130 750 -74 -80
at frequency of min. delay 500-600 Hz 600 - 1000 Hz 1000 - 2600 Hz 2600 - 2800 Hz G.714.16
9
Crosstalk
D/A to A/D A/D to D/A
CTRT CTTR
dB dB
AC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing. * Note: RxINC, refer to Control Register 2, address 0Fh.
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Zarlink Semiconductor Inc.
MT9196
AC Electrical Characteristics for Side-tone Path Characteristics 1 Absolute path gain Gain adjust = 0dB Sym. GAS1 GAS2 Min. -17.2 -14.7 Typ. -16.7 -14.2 Max. -16.2 -13.7 Units dB dB
Data Sheet
Test Conditions TxINC, RxINC both 0* TxINC, RxINC both 1* M inputs to HSPKR outputs 1000 Hz SIDEA/u=0 SIDEA/u=1 from nominal relative measurements w.r.t. GAS1 & GAS2
All other settings (-9.96 to +9.96dB)
GAS GAS
-0.3 -0.3
+0.3 +0.3
dB dB
AC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing. * Note: RxINC and TxINC, refer to Control Register 2, address 0Fh.
AC Characteristics for Auxiliary Analog LoopbackPath Characteristics 1 Absolute gain for analog loopback from Auxiliary port. AUXin to HSPKR GAA1 GAA2 GAA3 GAA4 -3.1 -0.6 3.0 -9 -1.1 1.4 5.0 -7 0.9 3.4 7.0 -5 dB dB dB dB @1020 Hz
AC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing. * Note: RxINC, refer to Control Register 2, address 0Fh.
Sym.
Min.
Typ.
Max.
Units
Test Conditions
RxINC = 0* RxINC = 1*
AUXin to SPKR AUXin to AUXout
AC Electrical Characteristics for Ringer Tone Characteristics 1 Ringer Tone Output voltage (SPKR+ to SPKR-) Sym. VR0 VR-4 VR-8 VR-12 VR-16 VR-20 VR-24 VR-28 Typ. 6.0 3.79 2.39 1.51 951 600 379 239 Units Vp-p Vp-p Vp-p Vp-p mVp-p mVp-p mVp-p mVp-p Test Conditions Gain2 Gain1 Gain0 0 0 0 0 0 1 0 1 0 0 1 1 1 0 0 1 0 1 1 1 0 1 1 1 Gain3 = 0 load>34 ohms across SPKR
AC Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing.
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Zarlink Semiconductor Inc.
MT9196
Electrical Characteristics for Analog Outputs Characteristics 1 2 3 Earpiece load impedance Allowable Earpiece capacitive load Earpiece harmonic distortion Sym. EZL ECL ED Min. 260 Typ. 300 300 0.5 Max. Units ohms pF %
Data Sheet
Test Conditions across HSPKR each pin: HSPKR+, HSPKR-
300 ohms load across HSPKR (tol-15%), VO 693mVRMS, RxINC=1*, Rx gain=0dB across SPKR each pin SPKR+, SPKR-
4 5 6
Speaker load impedance Allowable Speaker capacitive load Speaker harmonic distortion
SZL SCL SD
34
40 300 0.5
ohms pF %
40 ohms load across SPKR (tol-15%), VO 6.2Vp-p, Rx gain=0dB
Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing. * Note: RxINC, refer to Control Register 2, address 0Fh.
Electrical Characteristics for Analog Inputs Characteristics 1 Input voltage without overloading CODEC at MIC+ at AUXin across M+/M-
Sym.
Min.
Typ.
Max.
Units
Test Conditions
VIOLM VIOLA VIOLH
1.63 0.580 1.63 0.580 2.90 1.03
Vp-p Vp-p Vp-p Vp-p Vp-p Vp-p
TxINC = 0, A/ = 0* TxINC = 1, A/ = 1* TxINC = 1, A/ = 0* TxINC = 1, A/ = 1* TxINC = 0, A/ = 0* TxINC = 1, A/ = 1* Tx filter gain=0dB setting
2
Input impedance
ZI ZIA
50 10
k k
M+/M-, MIC+ AUXin to VSS
Electrical Characteristics are over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing. * Note: TxINC and A/ and refer to Control Register 2, address 0Fh.
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Zarlink Semiconductor Inc.
MT9196
AC Electrical Characteristics - ST-BUS Timing (See Figure 12) Characteristics 1 2 3 4 5 6 7 8 9 C4i Clock Period C4i Clock High period C4i Clock Low period C4i Clock Transition Time F0i Frame Pulse Setup Time F0i Frame Pulse Hold Time DSTo Delay DSTi Setup Time DSTi Hold Time Sym. tC4P tC4H tC4L tT tF0iS tF0iH tDSToD tDSTiS tDSTiH 30 30 50 50 100 125 Min. Typ. 244 122 122 20 Max. Units ns ns ns ns ns ns ns ns ns
Data Sheet
Test Conditions
CL = 50pF, 1k load.*
Timing is over recommended temperature range & recommended power supply voltages. Typical figures are at 25 C and are for design aid only: not guaranteed and not subject to production testing. * Note: All conditions data-data, data-HiZ, HiZ-data.
tT tC4P C4i 70% 30% tDSToD
1 bit cell tC4H tC4L
tT
DSTo
70% 30% tDSTiS 70% 30% tT tF0iS tF0iH tT tDSTiH
DSTi
F0i
70% 30%
NOTE:
Levels refer to%VDD
Figure 12 - ST-BUS Timing Diagram
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Zarlink Semiconductor Inc.
MT9196
AC Electrical Characteristics - SSI BUS Synchronous Timing (see Figure 13) Characteristics 1 BCL Clock Period 2 BCL Pulse Width High 3 BCL Pulse Width Low 4 BCL Rise/Fall Time 5 Strobe Pulse Width 6 Strobe setup time before BCL falling 7 Strobe hold time after BCL falling 8 Dout High Impedance to Active Low from Strobe rising 9 Dout High Impedance to Active High from Strobe rising 10 Dout Active Low to High Impedance from Strobe falling 11 Dout Active High to High Impedance from Strobe falling 12 Dout Delay (high and low) from BCL rising 13 Din Setup time before BCL falling 14 Din Hold Time from BCL falling Sym. tBCL tBCLH tBCLL tR/tF tENW tSSS tSSH tDOZL tDOZH tDOLZ tDOHZ tDD tDIS tDIH 50 50 80 80 Min. 244 122 122 20 8 x tBCL tBCL-80 tBCL-80 90 90 90 90 90 Typ. Max. 1953 Units ns ns ns ns ns ns ns ns ns ns ns ns ns ns
Data Sheet
Test Conditions BCL=4096 kHz to 512 kHz BCL=4096 kHz BCL=4096 kHz Note 1 Note 1
CL=150 pF, RL=1K CL=150 pF, RL=1K CL=150 pF, RL=1K CL=150 pF, RL=1K CL=150 pF
Timing is over recommended temperature range & recommended power supply voltages. Typical figures are at 25C and are for design aid only: not guaranteed and not subject to production testing. NOTE 1: Not production tested, guaranteed by design.
tBCLH tR CLOCKin (BCL) 70% 30%
tBCL tF
tBCLL tDIS Din 70% 30% tDOZL Dout 70% 30% tDOZH tSSS STB 70% 30% NOTE: Levels refer to% VDD (CMOS I/O) tENW tSSH tDOLZ tDOHZ tDD tDIH
Figure 13 - SSI Synchronous Timing Diagram
39
Zarlink Semiconductor Inc.
MT9196
AC Electrical Characteristics - SSI BUS Asynchronous Timing (note 1) (see Figure 14) Characteristics 1 Bit Cell Period 2 Frame Jitter 3 Bit 1 Dout Delay from STB going high 4 Bit 2 Dout Delay from STB going high 5 Bit n Dout Delay from STB going high Sym. TDATA Tj tdda1 tdda2 tddan 600+ TDATA-Tj 600 + (n-1) x TDATA-Tj TDATA-Tj TDATA\2 +500ns-Tj +(n-1) x TDATA TDATA\2 +500ns+Tj +(n-1) x TDATA 600+ TDATA 600 + (n-1) x TDATA Min. Typ. 7812 3906 600 Tj+600 600 + TDATA+Tj 600 + (n-1) x TDATA+Tj TDATA+Tj Max. Units ns ns ns ns ns ns
Data Sheet
Test Conditions BCL=128 kHz BCL=256 kHz CL=150 pF, RL=1K CL=150 pF, RL=1K CL=150 pF, RL=1K n=3 to 8
6 Bit 1 Data Boundary 7 Din Bit n Data Setup time from STB rising
TDATA1 tSU
ns ns n=1-8
8 Din Data Hold time from STB rising
tho
ns
Timing is over recommended temperature range & recommended power supply voltages. Typical figures are at 25C and are for design aid only: not guaranteed and not subject to production testing. NOTE 1: Not production tested, guaranteed by design. Tj
STB
70% 30% tdda2 tdha1
Dout
tdda1 70% 30% Bit 1 TDATA1 tho tsu Bit 2 Bit 3 TDATA
Din
70% 30% TDATA/2 D1 TDATA D2 TDATA D3
NOTE: Levels refer to% VDD (CMOS I/O)
Figure 14 - SSI Asynchronous Timing Diagram
40
Zarlink Semiconductor Inc.
MT9196
AC Electrical Characteristics - Microport Timing (see Figure 15) Characteristics 1 2 3 4 5 6 7 8 9 10 Input data setup Input data hold Output data delay Serial clock period SCLK pulse width high SCLK pulse width low CS setup-Intel CS setup-Motorola CS hold CS to output high impedance Sym. tIDS tIDH tODD tCYC tCH tCL tCSSI tCSSM tCSH tOHZ 500 250 250 200 100 100 100 1000 500 500 Min. 100 30 100 Typ. Max. Units ns ns ns ns ns ns ns ns ns ns
Data Sheet
Test Conditions
CL = 150pF, RL = 1K *
CL = 150pF, RL = 1K
Timing is over recommended temperature range & recommended power supply voltages. Typical figures are at 25C and are for design aid only: not guaranteed and not subject to production testing. * Note: All conditions data-data, data-HiZ, HiZ-data.
41
Zarlink Semiconductor Inc.
MT9196
Data Sheet
2.0V 0.8V tIDS tIDH tCH SCLK tCSSI CS tCSSM tCH tCL
DATA INPUT DATA OUTPUT 2.0V 0.8V tODD 90% HiZ 10% Intel Mode = 0
tCYC
2.0V 0.8V tOHZ 2.0V 0.8V tCSH 2.0V 0.8V tCL tIDH DATA OUTPUT tIDS 2.0V DATA INPUT 0.8V NOTE: % refers to% VDD 2.0V 0.8V tCYC tODD 90% HiZ 10% Motorola Mode = 00
SCLK
Figure 15 - Serial Microport Timing Diagram
42
Zarlink Semiconductor Inc.
c Zarlink Semiconductor 2005. All rights reserved.
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